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Final Electrical Specifications
LT3467 1.1A Step-Up DC/DC Converter in ThinSOTTM with Integrated Soft-Start
June 2003
FEATURES
s s s s s s s s s s s
DESCRIPTIO
1.3MHz Switching Frequency Low VCESAT Switch: 330mV at 1.1A High Output Voltage: Up to 40V Wide Input Range: 2.4V to 16V Dedicated Soft-Start Pin 5V at 540mA from 3.3V Input 12V at 270mA from 5V Input Uses Small Surface Mount Components Low Shutdown Current: < 1A Pin-for-Pin Compatible with the LT1930 and LT1613 Low Profile (1mm) SOT-23 Package
The LT(R)3467 SOT-23 switching regulator combines a 42V, 1.1A switch with a soft-start function. Pin compatible with the LT1930, its low VCESAT bipolar switch enables the device to deliver high current outputs in a small footprint. The LT3467 switches at 1.3MHz, allowing the use of tiny, low cost and low height inductors and capacitors. High inrush current at start-up is eliminated using the programmable soft-start function. A single external capacitor sets the current ramp rate. A constant frequency current mode PWM architecture results in low, predictable output noise that is easy to filter. The high voltage switch on the LT3467 is rated at 42V, making the device ideal for boost converters up to 40V as well as SEPIC and flyback designs. The LT3467 can generate 5V at up to 540mA from a 3.3V supply or 5V at 450mA from four alkaline cells in a SEPIC design. The LT3467 is available in a low profile (1mm) 6-lead SOT-23 package.
, LTC and LT are registered trademarks of Linear Technology Corporation ThinSOT is a trademark of Linear Technology Corporation.
APPLICATIO S
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Digital Cameras White LED Power Supply Cellular Phones Medical Diagnostic Equipment Local 5V or 12V Supply TFT-LCD Bias Supply xDSL Power Supply
TYPICAL APPLICATIO
VIN 2.6V TO 4.2V L1 2.7H C1 4.7F 4 OFF ON 6 VIN
95
D1 1 SW 3 R2 133k R1 402k
EFFICIENCY (%)
SHDN LT3467 5 SS GND 2
C4 3.3pF
VOUT 5V 765mA if VIN = 4.2V, 540mA if VIN = 3.3V, 360mA if VIN = 2.6V
90 85 80 75 70 65 60 VIN = 2.6V VIN = 4.2V VIN = 3.3V
FB
C3 0.047F
C2 15F
C1, C2: X5R OR X7R, 6.3V D1: ON SEMICONDUCTOR MBRM120 L1: SUMIDA CR43-2R7
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55 50 0 100 200 300 400 500 600 700 800 900 IOUT (mA)
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Figure 1. Single Li-Ion Cell to 5V Boost Converter
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
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Efficiency
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LT3467
ABSOLUTE
(Note 1)
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RATI GS
PACKAGE/ORDER I FOR ATIO
TOP VIEW SW 1 GND 2 FB 3 6 VIN 5 SS 4 SHDN
VIN Voltage .............................................................. 16V SW Voltage ................................................- 0.4V to 42V FB Voltage .............................................................. 2.5V Current Into FB Pin .............................................. 1mA SHDN Voltage ......................................................... 16V Maximum Junction Temperature ......................... 125C Operating Temperature Range (Note 2) .. - 40C to 85C Storage Temperature Range ................. - 65C to 150C Lead Temperature (Soldering, 10 sec).................. 300C
ORDER PART NUMBER LT3467ES6
S6 PACKAGE 6-LEAD PLASTIC TSOT-23
S6 PART MARKING LTACH
TJMAX = 125C, JA = 256C/ W
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
The q denotes specifications which apply over the full operating temperature range, otherwise specifications are TA = 25C. VIN = 3V, VSHDN = VIN unless otherwise noted.
PARAMETER Minimum Operating Voltage Maximum Operating Voltage Feedback Voltage
q
CONDITIONS
MIN
TYP 2.2
MAX 2.4 16 1.270 1.280 50 2 1 0.05 1.6
UNITS V V V V nA mA A %/V MHz % %
1.230 1.220
1.255 10 1.2 0.01 0.01
FB Pin Bias Current Quiescent Current Quiescent Current in Shutdown Reference Line Regulation Switching Frequency Maximum Duty Cycle
(Note 3) VSHDN = 2.4V, Not Switching VSHDN = 0.5V, VIN = 3V 2.6V VIN 16V
q
1
q
1.3 94 10
88 87 1.4 0.8
Minimum Duty Cycle Switch Current Limit Switch VCESAT Switch Leakage Current SHDN Input Voltage High SHDN Input Voltage Low SHDN Pin Bias Current SS Charging Current VSHDN = 3V VSHDN = 0V VSS = 0.5V 2 At Minimum Duty Cycle At Maximum Duty Cycle (Note 4) ISW = 1.1A VSW = 5V 2.4
1.8 1.2 330 0.01
2.5 1.9 500 1 0.5
16 0 3
32 0.1 4.5
Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: The LT3467E is guaranteed to meet performance specifications from 0C to 70C. Specifications over the -40C to 85C operating temperature range are assured by design, characterization and correlation with statistical process controls.
Note 3: Current flows out of the pin. Note 4: See Typical Performance Characteristics for guaranteed current limit vs duty cycle.
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LT3467 TYPICAL PERFOR A CE CHARACTERISTICS
Quiescent Current vs Temperature
1.6 1.4 1.2
ISHDN (A)
1.0
IQ (mA)
0.8 0.6 0.4 0.2 0 -40 -25 -10 5 20 35 50 65 80 95 110 125 TEMPERATURE (C)
3467 G01
VFB (V)
Current Limit vs Duty Cycle
2.0 1.8 1.6 1.4
ILIM (A)
OSCILLATOR FREQUENCY (MHz)
TYPICAL TA = 25C GUARANTEED VCESAT 100mV /DIV TA = 85C
1.2 1.0 0.8 0.6 0.4 0.2 0 10 20 30 40 50 60 DC (%) 70 80 90
Soft-Start Current vs Soft-Start Voltage
6 5 TA = 25C 2.0 1.8 1.6
SWITCH CURRENT (A)
4 ISS (A) 3 2 1 0
0
50 100 150 200 250 300 350 400 450 500 VSS (mV)
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UW
TA = 25C
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FB Pin Voltage vs Temperature
1.26 1.25 1.24 1.23 1.22 1.21 1.20 -40 -25 -10 5 140 120 100 80 60 40 20 0 20 35 50 65 80 95 110 125 TEMPERATURE (C)
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SHDN Current vs SHDN Voltage
TA = 25C
0
2
4
6
8 10 12 VSHDN (V)
14
16
18
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Switch Saturation Voltage vs Switch Current
1.5 1.4 1.3 1.2 1.1 1.0
Oscillator Frequency vs Temperature
TA = -40C
SW CURRENT 200mA/DIV
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0.9 -50 -25
0
25
50
75
100
125
TEMPERATURE (C)
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Peak Switch Current vs Soft-Start Voltage
TA = 25C VSHDN 2V/DIV
Start-Up Waveform (Figure 1 Circuit)
1.4 1.2 1.0 0.8 0.6 0.4 0.2 0 0 50 100 150 200 250 300 350 400 450 500 VSS (mV)
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VOUT 1V/DIV
ISUPPLY 0.5A/DIV 0.5ms/DIV
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PI FU CTIO S
SW (Pin 1): Switch Pin. (Collector of internal NPN power switch) Connect inductor/diode here and minimize the metal trace area connected to this pin to minimize EMI. GND (Pin 2): Ground. Tie directly to local ground plane. FB (Pin 3): Feedback Pin. Reference voltage is 1.255V. Connect resistive divider tap here. Minimize trace area at FB. Set VOUT = 1.255V(1 + R1/R2). SHDN (Pin 4): Shutdown Pin. Tie to 2.4V or more to enable device. Ground to shut down. SS(Pin 5): Soft-Start Pin. Place a soft-start capacitor here. Upon start-up, 4A of current charges the capacitor to 1.255V. Use a larger capacitor for slower start-up. Leave floating if not in use. VIN (Pin 6): Input Supply Pin. Must be locally bypassed.
BLOCK DIAGRA
SS
VIN 6
A1
-
VOUT R1 (EXTERNAL) FB R2 (EXTERNAL)
RC CC
-
RAMP GENERATOR
SHUTDOWN
4 SHDN
3
FB 1.3MHz OSCILLATOR
Figure 2. Block Diagram
OPERATIO
The LT3467 uses a constant frequency, current-mode control scheme to provide excellent line and load regulation. Refer to the Block Diagram above. At the start of each oscillator cycle, the SR latch is set which turns on the power switch Q1. A voltage proportional to the switch current is added to a stabilizing ramp and the resulting sum is fed into the positive terminal of the PWM comparator A2. When this voltage exceeds the level at the negative input of A2, the SR latch is reset, turning off the power switch. The level at the negative input of A2 is set by the error amplifier A1, and is simply an amplified version of the difference between the feedback voltage and the reference voltage of 1.255V. In this manner, the error amplifier sets the correct peak current level to keep the output in regulation. If the error amplifier's output increases, more current is delivered to the output. Similarly, if the error
decreases, less current is delivered. The soft-start feature of the LT3467 allows for clean start-up conditions by limiting the rate of voltage rise at the output of comparator A1 which, in turn, limits the peak switch current. The softstart pin is connected to a reference voltage of 1.255V through a 250k resistor, providing 4A of current to charge the soft-start capacitor. Typical values for the softstart capacitor range from 10nF to 200nF. The LT3467 has a current limit circuit not shown in the Block Diagram. The switch current is constantly monitored and not allowed to exceed the maximum switch current (typically 1.4A). If the switch current reaches this value, the SR latch is reset regardless of the state of comparator A2. This current limit protects the power switch as well as the external components connected to the LT3467.
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250k 5 1.255V REFERENCE
+
1 SW COMPARATOR DRIVER A2 R S Q Q1
+
0.01
2 GND
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LT3467
APPLICATIONS INFORMATION
Duty Cycle The typical maximum duty cycle of the LT3467 is 94%. The duty cycle for a given application is given by: of the total switch current. For better efficiency, use similar valued inductors with a larger volume. Many different sizes and shapes are available from various manufacturers. Choose a core material that has low losses at 1.3 MHz, such as ferrite core.
Table 1. Inductor Manufacturers.
Sumida TDK Murata (847) 956-0666 (847) 803-6100 (714) 852-2001 www.sumida.com www.tdk.com www.murata.com
DC =
| VOUT | + | VD | - | VIN | | VOUT | + | VD | - | VCESAT |
Where VD is the diode forward voltage drop and VCESAT is in the worst case 330mV (at 1.1A) The LT3467 can be used at higher duty cycles, but it must be operated in the discontinuous conduction mode so that the actual duty cycle is reduced. Setting Output Voltage R1 and R2 determine the output voltage. Vout = 1.255V (1+ R1/R2) Switching Frequency and Inductor Selection The LT3467 switches at 1.3 MHz, allowing for small valued inductors to be used. 4.7H or 10H will usually suffice. Choose an inductor that can handle at least 1.2A without saturating, and ensure that the inductor has a low DCR (copper-wire resistance) to minimize I2R power losses. Note that in some applications, the current handling requirements of the inductor can be lower, such as in the SEPIC topology where each inductor only carries one half
Supply Current of Figure 1 During Startup without Soft-Start Capacitor
VOUT 1V/DIV
ISUPPLY 0.5A/DIV ISUPPLY 0.5A/DIV 0.1ms/DIV 0.5ms/DIV
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Soft-Start The soft-start feature provides a way to limit the inrush current drawn from the supply upon startup. An internal 250k resistor charges the external soft start capacitor to 1.255V. After the capacitor reaches 0.15V the rate of voltage rise at the output of the comparator A1 tracks the rate of voltage rise of the soft-start capacitor. This limits the inrush current drawn from the supply during startup. Once the part is shut down, the soft start capacitor is quickly discharged to 0.4V, then slowly discharged through the 250k resistor to ground. If the part is to be shut down and re-enabled in a short period of time while soft-start is used, you must ensure that the soft-start capacitor has enough time to discharge before re-enabling the part. Typical values of the soft-start capacitor range from 10nF to 200nF.
Supply Current of Figure 1 During Startup with 47nF Soft-Start Capacitor
VOUT 1V/DIV
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APPLICATIONS INFORMATION
CAPACITOR SELECTION Low ESR (equivalent series resistance) capacitors should be used at the output to minimize the output ripple voltage. Multi-layer ceramic capacitors are an excellent choice, as they have extremely low ESR and are available in very small packages. X5R dielectrics are preferred, followed by X7R, as these materials retain the capacitance over wide voltage and temperature ranges. A 4.7F to 15F output capacitor is sufficient for most applications, but systems with very low output currents may need only a 1F or 2.2F output capacitor. Solid tantalum or OSCON capacitors can be used, but they will occupy more board area than a ceramic and will have a higher ESR. Always use a capacitor with a sufficient voltage rating. Ceramic capacitors also make a good choice for the input decoupling capacitor, which should be placed as close as possible to the LT3467. A 1F to 4.7F input capacitor is sufficient for most applications. Table 2 shows a list of several ceramic capacitor manufacturers. Consult the manufacturers for detailed information on their entire selection of ceramic parts.
Table 2. Ceramic Capacitor Manufacturers
Taiyo Yuden AVX Murata (408) 573-4150 (803) 448-9411 (714) 852-2001 www.t-yuden.com www.avxcorp.com www.murata.com
LOAD CURRENT 100mA/DIV AC COUPLED VOUT 200mV/DIV AC COUPLED
The decision to use either low ESR (ceramic) capacitors or the higher ESR (tantalum or OSCON) capacitors can affect the stability of the overall system. The ESR of any capacitor, along with the capacitance itself, contributes a zero to the system. For the tantalum and OSCON capacitors, this zero is located at a lower frequency due to the higher value of the ESR, while the zero of a ceramic capacitor is at a much higher frequency and can generally be ignored. A phase lead zero can be intentionally introduced by placing a capacitor (C4) in parallel with the resistor (R1) between VOUT and VFB as shown in Figure 1. The frequency of the zero is determined by the following equation. Z = 1 2 * R1* C 4
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By choosing the appropriate values for the resistor and capacitor, the zero frequency can be designed to improve the phase margin of the overall converter. The typical target value for the zero frequency is between 35kHz to 55kHz. Figure 3 shows the transient response of the stepup converter from Figure 8 without the phase lead capacitor C4. Although adequate for many applications, phase margin is not ideal as evidenced by 2-3 "bumps" in both the output voltage and inductor current. A 22pF capacitor for C4 results in ideal phase margin, which is revealed in Figure 4 as a more damped response and less overshoot.
LOAD CURRENT 100mA/DIV AC COUPLED
VOUT 200mV/DIV AC COUPLED
IL2 5A/DIV AC COUPLED 20s/DIV
3467 F03
Figure 3. Transient Response of Figure 8's Step-Up Converter without Phase Lead Capacitor
IL2 5A/DIV AC COUPLED 20s/DIV
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Figure 4. Transient Response of Figure 8's Step-Up Converter with 22pF Phase Lead Capacitor
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APPLICATIONS INFORMATION
DIODE SELECTION A Schottky diode is recommended for use with the LT3467. The Philips PMEG 2005 is a very good choice. Where the switch voltage exceeds 20V, use the PMEG 3005 (a 30V diode). Where the switch voltage exceeds 30V, use the PMEG 4005 (a 40V diode). These diodes are rated to handle an average forward current of 0.5A. In applications where the average forward current of the diode exceeds 0.5A, a Philips PMEG 2010 rated at 1A is recommended. For higher efficiency, use a diode with better thermal characteristics such as the On Semiconductor MBRM120 (a 20V diode) or the MBRM140 (a 40V diode). SETTING OUTPUT VOLTAGE To set the output voltage, select the values of R1 and R2 (see Figure 1) according to the following equation.
V R1 = R2 OUT - 1 1.255V
A good value for R2 is 13.3k which sets the current in the resistor divider chain to 1.255V/13.3k = 94A. LAYOUT HINTS The high speed operation of the LT3467 demands careful attention to board layout. You will not get advertised performance with careless layout. Figure 5 shows the recommended component placement.
D1 VOUT C2
1 2
L1
C1 VIN
6 5 4
CSS SS SHDN
GND
3
FB R2 R1
C3
VOUT
3467 F05
Figure 5. Suggested Layout
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Compensation--Theory Like all other current mode switching regulators, the LT3467 needs to be compensated for stable and efficient operation. Two feedback loops are used in the LT3467: a fast current loop which does not require compensation, and a slower voltage loop which does. Standard Bode plot analysis can be used to understand and adjust the voltage feedback loop. As with any feedback loop, identifying the gain and phase contribution of the various elements in the loop is critical. Figure 6 shows the key equivalent elements of a boost converter. Because of the fast current control loop, the power stage of the IC, inductor and diode have been replaced by the equivalent transconductance amplifier gmp. gmp acts as a current source where the output current is proportional to the VC voltage. Note that the maximum output current of gmp is finite due to the current limit in the IC. From Figure 6, the DC gain, poles and zeroes can be calculated as follows: 2 Output Pole: P1= 2 * *RL * C OUT 1 Error Amp Pole: P2 = 2 * *RO * C C 1 Error Amp Zero: Z1= 2 * *RC * C C 1 1.255 * gma * RO * gmp * RL * DC GAIN: A = 2 VOUT 1 ESR Zero: Z2 = 2 * * RESR * C OUT RHP Zero: Z3 = VIN * RL
2 2
2 * * VOUT * L f High Frequency Pole: P3 > S 3 1 Phase Lead Zero: Z4 = 2 * * R1* C PL 1 Phase Lead Pole: P4 = R1* R2 2 * * C PL * R1 + R2
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APPLICATIONS INFORMATION
Table 3. Bode Plot Parameters
-
gmp VOUT CPL RESR COUT R1 RL VC RC CC RO CC: COMPENSATION CAPACITOR COUT: OUTPUT CAPACITOR CPL: PHASE LEAD CAPACITOR gma: TRANSCONDUCTANCE AMPLIFIER INSIDE IC gmp: POWER STAGE TRANSCONDUCTANCE AMPLIFIER RC: COMPENSATION RESISTOR RL: OUTPUT RESISTANCE DEFINED AS VOUT DIVIDED BY ILOAD(MAX) RO: OUTPUT RESISTANCE OF gma R1, R2: FEEDBACK RESISTOR DIVIDER NETWORK RESR: OUTPUT CAPACITOR ESR
+
gma
1.255V REFERENCE
-
R2
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Figure 6. Boost Converter Equivalent Model
The Current Mode zero is a right half plane zero which can be an issue in feedback control design, but is manageable with proper external component selection. Using the circuit of Figure 1 as an example, the following table shows the parameters used to generate the Bode plot shown in Figure 7.
50 40 30 20
GAIN (dB)
10 0 -10 -20 -30 -40 -50 100 GAIN PHASE 1k 10k 100k FREQUENCY (Hz)
Figure 7.Bode Plot of 3.3V to 5V Application
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Parameter RL COUT RESR RO CC CPL RC R1 R2 VOUT VIN gma gmp L fS
Value 10.4 15 10 0.4 60 3.3 100 402 133 5 3.3 35 7.5 2.7 1.3
Units F m M pF pF k k k V V mho mho H MHz
Comment Application Specific Application Specific Application Specific Not Adjustable Not Adjustable Adjustable Not Adjustable Adjustable Adjustable Application Specific Application Specific Not Adjustable Not Adjustable Application Specific Not Adjustable
+
From Figure 7, the phase is -138 when the gain reaches 0dB giving a phase margin of 42. This is more than adequate. The crossover frequency is 37kHz.
0 -45 -90 -135
PHASE (DEG)
-180 -225 -270 -315 -360 -405 -450 1M
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TYPICAL APPLICATIO S
Lithium-Ion to 6V Step-Up DC/DC Converter
VIN 2.7V TO 4.2V C1 2.2F 4 5 C4 0.047F L1 2.2H 6 VIN SHDN LT3467 SS GND 2 1 SW 3 R2 133k C2 15F D1 R1 501k VOUT 6V 275mA AT VIN = 2.7V 490mA AT VIN = 3.8V 590mA AT VIN = 4.2V
SHDN
EFFICIENCY (%)
FB
C1, C2: X5R OR X7R, 6.3V D1: ON SEMICONDUCTOR MBRM120 L1: SUMIDA CR43-2R2
4V TO 6.5V C1 2.2F SHDN 4-CELL BATTERY C4 0.047F 6
C1, C3: X5R or X7R, 10V C2: X5R or X7R, 6.3V D1: PHILIPS PMEG 2010 L1, L2: MURATA LQH32CN100K33L
5V to 40V Boost Converter
L1 2.7H C1 4.7F SHDN 4 6 VIN SHDN LT3467 5 SS GND 2 1 SW 3 R2 13.3k R1 412k C2 1F D1 VOUT 40V 20mA
VIN 5V
FB
C3 0.1F
C1: X5R or X7R, 6.3V C2: X5R or X7R, 50V D1: ON SEMICONDUCTOR, MBRM140 L1: SUMIDA CD43-2R7
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95 90 85 80 75 70 65 60 VIN = 2.7V VIN = 4.2V VIN = 3.8V
C3 1.8pF
3467 TA01
55 50 0 100 200 300 400 IOUT (mA) 500 600 700
3467 TA01b
4-Cell to 5V SEPIC Converter
L1 10H 1 255k C5 4.7pF L2 10H C3 1F D1
VIN SW 4 SHDN LT3467 3 5 FB SS GND 2
VOUT 5V 325mA AT VIN = 4V 400mA AT VIN = 5V 450mA AT VIN = 6.5V C2 10F
84.5k
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15V Dual Output Converter with Output Disconnect
VIN 5V L1 10H C1 2.2F OFF ON 4 5 C6 0.047F 6 VIN SHDN LT3467 SS GND 2 D3 R4 1 D4 FB 1 SW 3 R2 13.3k C3 2.2F
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C4 1F
D1 15V 100mA
C5 1F
R3 1 D2
R1 147k C2 2.2F
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C1: X5R or X7R, 6.3V C2 TO C5: X5R or X7R, 16V D1 TO D4: PHILIPS PMEG 2005 L1: SUMIDA CR43-100
-15V 100mA
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TYPICAL APPLICATIO S
9V, 18V, -9V Triple Output TFT-LCD Bias Supply with Soft-Start
D1 D2 C3 0.1F VIN 3.3V L1 4.7H C1 2.2F 4 5 3.3V 0V C7 0.1F 6 VIN SHDN LT3467 SS GND 2 C2 0.1F D4 D3 C6 1F FB 1 SW 3 R1 124k C5 10F R2 20k
-9V OUTPUT 5V/DIV
VSHDN
C1: X5R OR X7R, 6.3V C2,C3, C5, C6: X5R OR X7R, 10V C4: X5R OR X7R, 25V D1 TO D4: PHILIPS BAT54S OR EQUIVALENT D5: PHILIPS PMEG 2005 L1: PANASONIC ELT5KT4R7M
8V, 23V, -8V Triple Output TFT-LCD Bias Supply with Soft-Start
D1 C3 0.1F L1 4.7H C1 2.2F VSHDN 4 5 3.3V 0V C9 0.1F 6 VIN SHDN LT3467 SS GND 2 C2 0.1F D5
2ms/DIV
VIN 3.3V
1 SW 3 R1 113k
FB
C1: X5R OR X7R, 6.3V C2 TO C4, C7, C8: X5R OR X7R, 10V C5: X5R OR X7R, 16V C6: X5R OR X7R, 25V D1 TO D6: PHILIPS BAT54S OR EQUIVALENT D7: PHILIPS PMEG 2005 L1: PANASONIC ELT5KT4R7M
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18V 10mA C4 1F
D5 9V 220mA
9V OUTPUT 5V/DIV
Start-Up Waveforms
18V OUTPUT 10V/DIV
IL1 0.5A/DIV 2ms/DIV
-9V 10mA
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D2 C4 0.1F D7
D3 C5 0.1F
D4 C6 1F
23V 10mA
Start-Up Waveforms
8V OUTPUT 5V/DIV -8V OUTPUT 5V/DIV
8V 270mA
C7 10F R2 21k
23V OUTPUT 10V/DIV
IL1 0.5A/DIV
D6
C8 1F
-8V 10mA
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PACKAGE DESCRIPTIO
0.62 MAX
0.95 REF
3.85 MAX 2.62 REF
RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR
0.20 BSC 1.00 MAX DATUM `A'
0.30 - 0.50 REF NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193 0.09 - 0.20 (NOTE 3)
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S6 Package 6-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1636)
2.90 BSC (NOTE 4) 1.22 REF 1.4 MIN 2.80 BSC 1.50 - 1.75 (NOTE 4) PIN ONE ID 0.95 BSC 0.30 - 0.45 6 PLCS (NOTE 3) 0.80 - 0.90 0.01 - 0.10 1.90 BSC
S6 TSOT-23 0302
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TYPICAL APPLICATIO S
VIN 5V L1 4.7H C1 2.2F SHDN 4 5 C3 0.047F C1: X5R OR X7R, 6.3V C2: X5R OR X7R, 16V D1: PHILIPS PMEG 2010 L1: SUMIDA CR43-4R7 *OPTIONAL 6 VIN SHDN LT3467 SS GND 2 1 SW 3 R2 13.3k D1 R1 115k
EFFICIENCY (%)
Figure 8. 5V to 12V, 270mA Step-Up Converter
RELATED PARTS
PART NUMBER LT1371/LT1371HV LT1613 LT1615/LT1615-1 LT1618 LTC1700 LTC1871 LT1930/LT1930A LT1946/LT1946A LT1961 LTC3400/LTC3400B LTC3401 LTC3402 LTC3464 DESCRIPTION 3A (ISW), 500kHz, High Efficiency Step-Up DC/DC Converter 550mA (ISW), 1.4MHz, High Efficiency Step-Up DC/DC Converter 300mA/80mA (ISW), High Efficiency Step-Up DC/DC Converter 1.5A (ISW), 1.25MHz, High Efficiency Step-Up DC/DC Converter No RSENSETM, 530kHz, Synchronous Step-Up DC/DC Controller Wide Input Range, 1MHz, No RSENSE Current Mode Boost, Flyback and SEPIC Controller 1A (ISW), 1.2MHz/2.2MHz, High Efficiency Step-Up DC/DC Converter 1.5A (ISW), 1.2MHz/2.7MHz, High Efficiency Step-Up DC/DC Converter with Soft-Start 1.5A (ISW), 1.25MHz, High Efficiency Step-Up DC/DC Converter 600mA (ISW), 1.2MHz, Synchronous Step-Up DC/DC Converter 1A (ISW), 3MHz, Synchronous Step-Up DC/DC Converter 2A (ISW), 3MHz, Synchronous Step-Up DC/DC Converter 85mA (ISW), High Efficiency Step-Up DC/DC Converter with Integrated Schottky and PNP Disconnect COMMENTS VIN: 2.7V to 30V, VOUT(MAX): 35V/42V, IQ: 4mA, ISD: <12A, DD,TO220-7, S20 Package 90% Efficiency, VIN: 0.9V to 10V, VOUT(MAX): 34V, IQ: 3mA, ISD: <1A, ThinSOT Package VIN = 1V to 15V, VOUT(MAX): 34V, IQ: 20A, ISD: <1A, ThinSOT Package 90% Efficiency, VIN: 1.6V to 18V, VOUT(MAX): 35V, IQ: 1.8mA, ISD: <1A, MS Package 95% Efficiency, VIN: 0.9V to 5V, IQ: 200A, ISD: <10A, MS Package 92% Efficiency, VIN: 2.5V to 36V, IQ: 250A, ISD: <10A, MS Package High Efficiency, VIN: 2.6V to 16V, VOUT(MAX: 34V, IQ: 4.2mA/5.5mA, ISD: <1A, ThinSOT Package High Efficiency, VIN: 2.45V to 16V, VOUT(MAX): 34V, IQ: 3.2mA, ISD: <1A, MS8 Package 90% Efficiency, VIN: 3V to 25V, VOUT(MAX): 35V, IQ: 0.9mA, ISD: 6A, MS8E Package 92% Efficiency, VIN: 0.85V to 5V, VOUT(MAX): 5V, IQ: 19A/300A, ISD: <1A, ThinSOT Package 97% Efficiency, VIN: 0.5V to 5V, VOUT(MAX): 5.5V, IQ: 38A, ISD: <1A, MS Package 97% Efficiency, VIN: 0.5V to 5V, VOUT(MAX): 5.5V, IQ: 38A, ISD: <1A, MS Package VIN: 2.3V to 10V, VOUT(MAX): 34V, IQ: 25A, ISD: <1A, ThinSOT Package
No RSENSE is a trademark of Linear Technology Corporation.
12
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900
q
FAX: (408) 434-0507 q www.linear.com
U
5V to 12V Efficiency
VOUT 12V 270mA C4* 22pF
90 85 80
FB
C2 10F
75 70 65 60 55 50 0 50 100 150 200 IOUT (mA) 250 300 350
3467 TA06a
3467 TA06b
3467i LT/TP 0603 1K * PRINTED IN USA
(c) LINEAR TECHNOLOGY CORPORATION 2003

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